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A Neural-Network-Based Non-linear Interference
Cancellation Scheme for Wireless IoT Backhaul
with Dual-Connectivity
Huiliang Zhang*, Zhonglong Wang*, Fei Qin†, Meng Ma*, and Jianhua Zhang*
*Department of Electronics, Peking University, Beijing, 100871, China
†vivo Mobile Communication Technology Co., Ltd, Beijing, China
E-mail:mam@pku.edu.cn
Abstract—In this paper, we consider an Internet of Things
(IoT) wireless network using Long Term Evolution (LTE) cellular
system as backhaul. To provide high throughput, by using dual-
connectivity technique, the IoT gateway simultaneously connects
to two evolved Node Bs (eNBs) on two carriers, one for downlink
and the other for uplink. As a result, the receive link will
be severely interfered by the harmonic interference (HI) and
intermodulation (IM) components caused by the imperfections of
power amplifier (PA) and in-phase/quadrature (I/Q) modulator.
To solve this problem, in this paper, an neural-network (NN)-
based non-linear interference cancellation scheme is proposed for
dual-connectivity IoT gateway. In the proposed scheme, the non-
linear interference is first reconstructed by using the transmit
signal and the trained NN in baseband, and then subtracted from
the received signal in digital domain at receiver. The NN precisely
models the link behavior from the baseband transmitter to the
baseband receiver, including all the linear and non-linear effect.
Additionally, the NN can be used to reconstruct and cancel not
only the HI, but also the IM components of the mirror-frequency
interference (MFI) caused by I/Q imbalance, and direct current
(DC) bias caused by local oscillator (LO) leakage. To evaluate
the performance of the proposed scheme, a hardware prototype
is designed and implemented. Experimental results show that the
proposed scheme has a superior performance in dual-connectivity
system compared with the traditional non-linear interference
cancellation scheme using polynomial (PM) model.
Index Terms—Iot gateway, neural-network, dual-connectivity,
intermodulation, non-linear interference
I. INTRODUCTION
Internet of Things (IoT) is a set of technologies that can
interconnect anything, from daily life objects to more sophisti-
cated networked devices. As the number of devices connected
to the Internet is growing substantially, a massive number of
small packets are generated and transmitted via wireless access
networks, thus posing a great challenge for wireless networks to
sustain high throughput performance. One of the key problem
is that the throughput performance degrades dramatically for
small packets, since the headers of transport protocol and
packet scheduling are usually substantial, thus leading to more
transmission resources used for data that is not directly visible
for applications [1]. IoT wireless backhaul is an effective way
to solve this problem, in which the wireless IoT gateway first
collects data from IoT devices, and then forwards the data via
the backhaul link connected to end users or IoT clouds [2], [3].
As cellular networks have already be almost ubiquitous, they
can be utilized to provide IoT traffic access to the Internet
regardless of their location. In this paper, we consider to utilize
Long Term Evolution (LTE) network as wireless backhaul.
Though a single IoT device usually does not generate a sig-
nificant amount of traffic, but the number of IoT devices in an
IoT backhaul network can be massive, thus leading to a massive
amount of aggregated traffic data at the IoT gateway. To provide
high throughput for the backhaul link, carrier aggregation
technique can be adopted, where mobile stations are able to
consume radio resources of several serving cells simultane-
ously, and utilize the potentially aggregate bandwidth across
all of them [4], thus boosting capacity of the backhaul link.
Additionally, the emerging dual-connectivity [5] is regarded as
an attractive access mechanism in heterogeneous networks; in
LTE network, by using dual-connectivity technique, the mobile
stations are allowed to be connected simultaneously to two
evolved Node Bs (eNBs) over two carriers, thus significantly
improving the throughput and robustness.
However, when the IoT gateway works in dual-connectivity
mode, the receive link will be severely interfered by harmonic
interference (HI) caused by the non-linear effect of its own
power amplifier (PA). For example, if the gateway transmitter
works at 1.8 GHz, and the receiver works at 3.6 GHz, the
even harmonic would directly leak to its own receiver. Addi-
tionally, the other concern is the transmitter imperfections of
in-phase/quadrature (I/Q) modulator, which leads to amplitude
and phase mismatching between the I/Q signal branches of the
modulator in direct-conversion radios [6]. These impairments
introduce mirror-frequency interference (MFI), direct current
(DC), and extra intermodulation (IM) components at the output
of PA, which will dramatically degrade the detection perfor-
mance [7] and deteriorate the bit error rate. In addition, the RF
chain from transmitter to receiver contains not only non-linear
devices, but also linear devices, such as pulse shaping filters
and micro strip lines. Hence, the system can be modeled as
a Hammerstein model [8], where the non-linear part is used
for modeling transmitter PA, and the linear part is used for
modeling channel between transmitter and receiver.
So far, most of studies on the non-linear interference can-
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cellation have been oriented towards the digital predistortion
at transmitter to cancel the non-linear interference of PA with
modulator imperfections. The most general forms are described
by polynomial (PM) model and Volterra series [9], [10]; and
pilot symbol sequence in this models is usually utilized to
obtain parameter estimates. However, these models are found
to be effective for mildly non-linear, but not appropriate for
strongly non-linear. Additionally, some studies focus on the
joint cancellation for the non-linear effect of PA and I/Q
modulater. Contemporary solutions contain two-step processes
[11], [12], in which MFI and DC are considered first, followed
by the cancellation of HI for PA linearization. In [13], a real-
valued focused time-delay neural-network (NN) model has
been proposed to mitigate the distortions in one-step, which
simplifies the predistortion process, and has a strong adaptive
nature of behavioral modeling of PA. In [14], a NN-based
method is proposed to cancel the non-linear interference in
radio frequency (RF) chains, which leads to additional costs in
terms of power and hardware complexity.
In this paper, an NN-based non-linear interference cancel-
lation scheme is proposed for dual-connectivity IoT wireless
gateway system. In the proposed scheme, the non-linear can-
cellation interference can be split into two steps; the first is to
reconstruct the HI and IM components by using the transmit
signal and the trained NN in baseband, and the second is to
subtract them from the received signal in digital domain at
receiver. Additionally, the proposed scheme addresses both the
non-linear and linear effects over the channel from transmitter
to receiver. To evaluate the performance of the proposed
scheme, a hardware prototype is designed and implemented.
Experimental results show that outstanding performance can
be achieved by using the proposed NN-based cancellation,
compared with that of using traditional PM model.
The remainder of this paper is organized as follows. Section
II introduces the system model of IoT wireless gateway work-
ing in dual-connectivity mode with a non-linear interference
canceller. Section III describes the design of NN-based non-
linear interference cancellation scheme. In Section IV, the
hardware prototype, measurement setup and conditions are
introduced, and the performance of the proposed scheme is
also presented and discussed. Finally, conclusions are drawn
in Section V .
II. SYSTEM MODEL
In order to provide high throughput for backhaul link, an
IoT gateway is simultaneously connected to two eNBs on two
carries, one for uplink and the other for downlink by using
dual-connectivity as shown in Fig. 1. f1and f2are the carriers
frequency of uplink and downlink for backhaul, respectively.
When f2≈2f1, the IoT gateway’s receiver would be severely
interfered by the HI caused by the non-linear effect of its
own PA, because the even harmonic interference would directly
leak from the transmit chain to the receive chain without any
propagation loss. Additionally, the MFI and LO caused by
I/Q imbalance also inevitably degrade the quality of desired
signal. A basic block diagram of an IoT gateway with dual-
Fig. 1. IoT gateway connected to two eNBs on two carries and IoT devices.
connectivity mode is shown in Fig. 2. The transmit signal in
digital domain can be expressed as
X(n)=I(n)+iQ(n),(1)
where i=√−1, and I(n)and Q(n)are the I/Q components
of the baseband digital signal. After digital modulation and
up frequency conversion, X(n)is converted into RF signal
˜
Xmod (t), and non-linear components are introduced due to
the imperfection of I/Q mixer which leads to DC offsets and
I/Q imbalance. Thus, the RF signal can be represented as
˜
Xmod (t)=(
˜
I(t)+Ci) cos(ω1t)−α(˜
Q(t)+Cq)sin(ω1t+ϕ),
(2)
where ˜
I(t)and ˜
Q(t)are the I/Q components of the baseband
signal after pulse shaping, ω1represents the angular frequency
of the carrier, and Ciand Cqare the DC offsets in the
I and Q channels, respectively. αand ϕare the gain and
phase imbalances between the I and Q channels. At the end
of transmitter RF chain, PA also introduces non-linear effect,
which can be expressed as
˜
Xout(t)=Gup ×fup [˜
Xmod ],(3)
where Gup and function fup represent the gain and the non-
linear transfer function of PA, respectively.
When f2is twice of f1, the receive link will be severely
interfered by the HI and IM interference from its own non-
linearity [15].
At the receiver, the received HI can be expressed as
˜rst(t)=Hejϕ ˜
Xout +n(t),(4)
where Hand ϕdenote linear channel gain and phase rotation
coefficient, respectively. n(t)denotes the additive Gaussian
noise. As we only focus on HI and IM interference cancellation
in this paper, the desired signal is omitted in (4). The output
of a complete receiver in downlink at f2is given as
˜r(t)=Gdown ×fdown [˜rst(t)],(5)
where the function fdown and gdown are the downlink non-
linear function and gain of the PA at receiver, respectively;
then, the digital received signal r(n)can be obtain through
ADC. The goal of digital NN is to reconstruct an accurate
copy of r(n). The output of NN, denoted by ˜r(n), is then
subtracted from the received signal. Therefore, the residual
non-linear interference can be calculated by
ε(n)=r(n)−˜r(n).(6)
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Fig. 2. IoT gateway in dual-connectivity with one-step non-linear interference
cancellation scheme.
III. ANNN-BASED NON-LINEAR INTERFERENCE
CANCELLATION SCHEME
In this section, the design of NN-based non-linear inter-
ference cancellation scheme is detailed for dual-connectivity
IoT gateway system. Our aim is to cancel the HI and IM
components caused by the non-linear effect in PA, and the I/Q
imbalance from the received signal in digital domain.
Considering that NN is not primarily designed to operate
with complex signals while the transmit signal and received
HI are both in complex domain, a real-valued feed-forward
NN model, as shown in Fig. 3, is adopted in this paper. The
I/Q components of current samples are used as the inputs to
the NN, thus, each neuron of the hidden layer treats a linear
combination of I and Q components.
Fig. 3. Real-valued feed-forward NN model.
Usually, NN is composed of an input layer, hidden layers
and an output layers, and the number of hidden layers and
their corresponding neurons are commonly determined during
training of the network or by using empirical methods [16],[17].
According to the features of the digital signal used in IoT and
the approximation theorem that a feed-forward network with
a single hidden layer, containing a finite number of hidden
neurons, is a universal approximator for continuous functions
[18], we selected one hidden layer in this paper. The output of
each neuron is equal to the bias plus the sum of the products of
the input signals and corresponding weights, which is expressed
as [19]
dl
i(n)=
p
i=1
ωl
i,j xl−1
j(n)+bl
i,(7)
where ωl
i,j represents the weight connecting the j-th neuron of
the (l−1)-th layer to the i-th neuron at the l-th layer. xl−1
jis
the input signal from the previous (l−1)-th layer to the j-th
neuron, and bl
iis the bias of the i-th neuron at the l-th layer.
To model the non-linear effect and the linear channel from
PA to the receiver chain, we apply hyperbolic tangent sigmoid
[17] transfer function as activation function, which can be
written as
tansig(x)= 2
1+exp(−2x)−1.(8)
The output layer of the NN contains 2 neurons. The cost
function is calculated in batch mode during the forward pass
[17], and can be defined as
E=1
2N
N
n=1
[(Iout(n)−ˆ
Iout(n))2+(Qout (n)−ˆ
Qout(n))2],
(9)
where Iout(n)and Qout (n)are the I and Q components of
the desired output signals, while ˆ
Iout(n)and ˆ
Qout(n)are the
outputs of output layer.
The NN is trained by minimizing least square (LS) criterion
using Leven-Marquardt backpropagation algorithm [20], and
the training process stops when the NN satisfies the desired
modeling performance or reached the preset maximum epoch
or overtraining [16].
The reconstructed signals at the output of NN can be
expressed as
ˆr(n)=ˆ
Iout(n)+iˆ
Qout(n),(10)
which is then subtracted from the received signal in digital
domain to achieve non-linear interference cancellation. The
proposed scheme needs only the input and output data to adapt
to any imperfection in dual-connectivity system.
IV. EXPERIMENTAL MEASUREMENT SETUP,RESULTS AND
DISCUSSION
In order to verify the performance of the proposed interfer-
ence cancellation scheme, we implement a hardware prototype
for non-linear interference generation and cancellation.
We use quadrature phase shift keying (QPSK) modulated
orthogonal frequency division multiplexing (OFDM) signal as
the transmit signal, which is generated by using MATLAB,
and then downloaded into YunSDR. The YunSDR is a radio
platform consisting of FPGA (Xilinx Zynq SoC XC7Z020) and
AD9361, and can perform digital modulation, digital-to-analog
conversion, frequency up-conversion and PA. At the transmitter,
the transmit RF signal at the output of YunSDR is sent to
the PA (ZRL-2400LN+); then it is fed to YunSDR receiver
by a coaxial cable. The received signal is down-converted and
sampled by ADC, and stored to computer for offline analysis.
Additionally, the transmit and receive signal used as the input
and output data of NN, are obtained when the IoT backhaul
works in transmitting state and can capture the interference data
at f2without receiving the desired signal from receive link.
The received baseband data (Iout(n)and Qout(n)) are then
analyzed by using MATLAB. By using the transmit and receive
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TABLE I
NMSE PERFORMANCE COMPARISON FOR DIFFERENT TRANSMIT POWER
IN NN-BASED AND PM MODELS.
Transmitted
signal
power(dBm)
NMSE(dB)
NN-based
Optimal
Num.of neurons
NMSE(dB)
PM
9.50 -30.0792 200 -7.094206
7.36 -31.8119 200 -10.31424
6.14 -32.1645 200 -15.80482
5.12 -31.0917 130 -20.69239
3.16 -32.2692 150 -18.21896
signal as the input and output data of NN, the NN is trained
to approximate the non-linear behavior of the PA. The desired
modeling performance in terms of MSE and maximum epochs
are set to be 10−6and 100, respectively. Once the training
process stopped, the transmit signal can be applied to NN for
non-linear interference reconstruction.
The interference signal is continuously reconstructed using
the NN and then subtracted from received signal to eliminate
the non-linear interference. The NN-based model is retrained
and the parameters are updated periodically using a new set of
data to adapt time variant.
In this paper, 2048×5×2 independent samples of the input
and output signal are used for training, validation and testing
purpose. During each experiment, 65% data is used for training,
25% for the purpose of the validation process, and the rest 10%
is used for testing. The performance of the normalized-mean-
square error (NMSE) is then validated, and NMSE is given
by
NMSE = 10 log
⎛
⎜
⎜
⎝
N
n=1 |(r(n)−ˆr(n))|2
N
n=1 |r(n)|2
⎞
⎟
⎟
⎠
.(11)
Table I shows the NMSE performance of the NN-based
model compared with PM model for different transmit power.
The PM model which is used in non-linear interference formu-
lates the non-linearity in dual-connectivity as
r(n)=Hejϕ
∞
p=1
apCp−1
2p|X(n)|2p−2·X2(n).(12)
where 2pis the non-linearity order, and apis the coefficient
of PM model. In the PM scheme, the pilot symbol sequence
is required to obtain estimates of H,ϕand ap. The coefficient
apis calculated using LS algorithm.
The OFDM signal is modulated by a 2048-point inverse fast
fourier transform, and only 12 sub-carriers are used for trans-
mitting QPSK symbols. Thus, the bandwidth is approximate to
200 kHz, which is the same as that in NB-IoT system. Table
I shows that the proposed scheme keeps a better cancellation
capability and robustness than PM model for different transmit
power. This is because that the PM model is not appropriate for
TABLE II
MAIN NON-LINEAR COMPONENTS.
Non-linear
components
Frequency
(MHz) Main components
HI 6MHz Even harmonic
IM2(a) 0MHz IM component from
MFI, DC and odd harmonic of signal
IM2(b) -6MHz IM component from
MFI and even harmonic of MFI
IM2(c) 3MHz IM component from
DC and odd harmonic of signal
IM2(d) -3MHz IM component from
DC and odd harmonic of signal
strong non-linear behavior modeling, while NN has advantage
for modeling strongly non-linear system. In order to analyze
the non-linear components, power spectrum density (PSD) of
received OFDM signal is plotted in Fig. 4. It is shown that the
received non-linear components at 3.6 GHz contains not only
the HI component, but also various IM components, which
were analyzed in Table II.
Apparently, using PM model in (12) can only cancel the HI
component, but not the other IM components. However, for the
NN-based interference cancellation scheme, it has the potential
advantage to cancel all components in Table II. One can find
from Fig. 4 that the NN-based scheme makes a good match
not only on the frequency of HI, but also on the frequencies
of other IM components.
-10-8-6-4-20246810
Frequency (MHz)
-70
-60
-50
-40
-30
-20
-10
0
10
20
30
Power Spectrum Density (dB/Hz)
received signal
reconstructed signal by NN-based model
reconstructed signal by PM model
IM2(b)
IM2(d)
IM2(a)
IM2(c)
HI
Fig. 4. Power spectrum density (PSD) of received OFDM signal, reconstructed
signal from NN-based and PM models.
Finally, the waveforms of the received and reconstructed
non-linear interference are plotted in Fig. 5. It is shown that a
good match is achieved between the received and reconstructed
non-linear interference.
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2300 2310 2320 2330 2340 2350 2360 2370 2380 2390 2400
Samples
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
1.2
In-phase Components
received signal
reconstructed signal by NN-based model
2362 2364 2366 2368 2370
0.2
0.3
0.4
(a)
2300 2310 2320 2330 2340 2350 2360 2370 2380 2390 2400
Samples
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
1.2
Quadrature Components
received signal
reconstructed signal by NN-based model
2358 2360 2362 2364 2366
0.35
0.4
0.45
(b)
Fig. 5. Validation of NN model for OFDM signal output I and Q components
in time domain, (a) In-phase components, (b) Quadrature components.
V. C ONCLUSION
In this paper, we proposed an NN-based non-linear in-
terference cancellation scheme for IoT gateway with dual-
connectivity in baseband. The hardware prototype implemen-
tation and experimental results are also introduced. In the
proposed scheme, both the non-linear and linear effects in
system are precisely modeled by NN on baseband at the re-
ceiver. The non-linear interference is reconstructed by using the
transmit signal and the trained NN, and then subtracted from
the received signal in digital domain. The experimental results
have shown that the proposed scheme can effectively suppress
not only the HI components, but also the IM components from
MFI and DC bias.
ACKNOWLEDGMENT
This work was supported by the Program for Core tech-
nology tackling key problems of Dongguan City under grant
number 2019622109010, and the National Natural Science
Foundation of China under grant number 61671024.
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